We present a new, alternative approach to realize a wavelength swept light source with no fundamental limit to sweep speed. Amplified spontaneous emission (ASE) light alternately passes a cascade of optical gain elements and tunable optical bandpass filters. We show that for high sweep speeds, the control signal for the different filters has to be applied with a defined, precise phase delay on the order of nanoseconds, to compensate for the light propagation time between the filters and ensure optimum operation. At a center wavelength of 1300 nm sweep rates of 10 kHz, 100 kHz and 340 kHz over a sweep range of 100 nm full width and an average power of 50 mW are demonstrated. For application in optical coherence tomography (OCT), an axial resolution of 12 µm (air), a sensitivity of 120 dB (50 mW) and a dynamic range of 50 dB are achieved and OCT imaging is demonstrated. Performance parameters like coherence properties and relative intensity noise (RIN) are quantified, discussed and compared to the performance of Fourier Domain Mode Locked (FDML) lasers. Physical models for the observed difference in performance are provided.
© 2009 OSA
Optical Coherence Tomography (OCT) is a novel biomedical imaging technique for visualizing tissue microstructure in vivo . While the first OCT systems used the so called time domain detection (TD-OCT), the demand for higher imaging speeds was one of the main reasons for focusing research on frequency domain OCT (FD-OCT) [2, 3]. At equivalent imaging parameters, FD-OCT provides higher sensitivity [4–6]. As an alternative to spectrometer based FD-OCT systems, FD-OCT systems using rapidly wavelength swept narrow-band light sources (swept source – SS-OCT or optical frequency domain imaging – OFDI ) offer several potential advantages: (i) The realization of dual balanced detection is easier, suppressing noise and auto-correlation artifacts; (ii) SS-OCT systems often have a longer ranging depth because of the narrow linewidth and long instantaneous coherence length of the applied laser light sources; (iii) SS-OCT/OFDI systems suffer less from fringe washout caused by sample motion or by rapid scanning of structures with high aspect ratio, and so the performance with respect to signal fading, spatial distortion and blurring can be improved .
Since the first demonstration of high speed SS-OCT, huge efforts have been made to push the wavelength sweep repetition rate of the OCT light sources [9–11]. For standard wavelength swept lasers, the length of the resonator limits the maximum wavelength sweep speed (and therefore imaging speed), because the number of possible roundtrips of light in the resonator is reduced and the build-up of saturated lasing from amplified spontaneous emission (ASE) is impeded . Minimizing the laser resonator length enables higher sweep speeds but also enlarges the discrete resonator mode spacing [12, 13]. This can increase intensity noise and ultimately limit the maximum OCT ranging depth, if the laser cavity length is reduced down into the millimeter range.
One solution to this problem is the application of optical circuits without feedback. These resonator-less designs can be broadband light sources with a tunable optical bandpass filter for post-filtering . Although post-filtering is widely used in all kinds of hyperspectral imaging and microscopy applications, the tight instantaneous bandwidth requirement in OCT of ~0.1 nm causes a huge power loss due to the high finesse filtering . Therefore an additional post-amplification can be used to provide sufficient levels of output power. The process of post-amplification of filtered ASE was demonstrated in a very rapidly swept laser source , where the tuning rate was above the single roundtrip limit and the laser did not have optical feedback anymore. The problem in this setup was the high ASE background of about 2 mW compared to <0.5 mW of the desired wavelength swept narrow-band signal.
With the demonstration of Fourier Domain Mode Locked Lasers (FDML) , the physical limitations of the maximum achievable sweep speed could be overcome and additionally, high output power levels at low ASE background can be achieved. In FDML lasers, an optical delay line in the laser resonator enables to drive the tunable optical bandpass filter synchronously to the round trip time of light in the resonator. The optical bandpass filter can be a rotating polygon mirror in combination with an optical grating [15, 16], a tunable fiber Fabry-Perot filter [17–21] or a tunable active gain element . Record imaging speeds of up to 370.000 lines/s , high phase stability  and long ranging depths  have been demonstrated. FDML lasers have successfully been applied for numerous imaging, sensing and ranging applications [11, 13, 15, 19, 23–37].
The presented wavelength swept ASE source is a new, alternative approach to realize a wavelength swept light source with high power, low ASE and rapid sweeping operation. It should be underlined that it is not a real laser, since no resonator and optical feedback exists. In order to achieve a sufficient output power level and sensitivity for OCT imaging, ASE light alternately passes a linear cascade of multiple different gain elements and multiple different filter elements. The concept is related to post-filtering and amplification. However, in order to prevent excessive amplification of unfiltered ASE background, the light must be filtered prior to each new amplification step, so several different filters are required. A crucial factor for optimum performance is to drive the different wavelength filters with an accurate phase delay, to compensate for the light transit time between the filters. Using this technique, no fundamental limit to the sweep speed exists, just like in the case of FDML lasers. However, unlike FDML lasers, the demonstrated setup is fundamentally not limited to discrete drive frequencies. It enables high output power over a continuous range of drive frequencies, limited only by the mechanical response of the filter. Furthermore, the concept is not limited to periodic wavelength sweeps as in FDML. Arbitrary sweep functions can be generated. Additionally, no km long, optical delay fiber is required as in FDML. This reduces cost, especially at wavelengths, where expensive specialty fiber has to be used, e.g. for FDML at 1060 nm. Regarding rapidly swept light sources at 800 nm, the high loss of ~3 dB/km and large chromatic dispersion in optical fiber make FDML operation difficult. Therefore the wavelength swept ASE source could be a promising alternative for high speed SS-OCT imaging in particular in the 800 nm or 1060 nm wavelength range.
2. Experimental setup and operation
2.1 The optical setup
Figure 1(a) shows the fiber-based setup of the demonstrated wavelength swept ASE source at 1300 nm. ASE from the first semiconductor optical amplifier (SOA 1, Covega Corp.) propagates through an optical circulator (CIR, 2 to 3) and is filtered by a piezo actuated, fiber-based tunable Fabry-Perot filter (FFP-TF 1, Lambda Quest, LLC.). The filtered light is directed back to SOA 1 by the circulator (1 to 2). Therefore SOA 1 is used as source for ASE light and simultaneously as a first amplification stage.
The resulting spectrum has to be filtered again with another fiber-based Fabry-Perot filter (FFP-TF 2, Lambda Quest, LLC.) to remove ASE background before the light can be boosted with SOA 2 (Covega Corp.). The polarization state is adjusted with two polarization controllers (PC1 and PC2) because of the polarization dependent gain in the SOAs. The circulator and several isolators (ISO) prevent an amplification of reflected ASE.
2.2 The filter control drive waveforms
An arbitrary waveform driver generates two sinusoidal, locked AC voltage signals of same frequency fdrive=ω/(2π) with a defined, adjustable phase shift with respect to each other. This phase shifted drive signal is very crucial to account for the light transit time τtrans between FFP-TF 1 and FFP-TF 2. Another effect which has to be compensated is the different phase response ∆ϕR of both filters  (including contributions of the electronic drivers) at the drive frequency fdrive=ω/(2π). Both signals are amplified and superimposed to two independent controllable DC-voltages U0,1 and U0,2 determining the center of the wavelength sweep. The resulting waveforms U1(t)=U0,1+A1∙sin(ωt-ϕ1) and U2(t)=U0,2+A2∙sin(ωt-ϕ2) are applied to drive FFP-TF 1 and FFP-TF 2. Because the FFP-TF filters are not identical with respect to their free spectral range (FSR) at zero voltage and the voltage response of the piezo actuator, we investigate the optimum drive parameter values in the following. To calculate the required drive waveforms, we consider λk(mk,t) to be the transmission maximum of FFP-TF(k), i.e. the kth filter in the sequence. The FFP-TF is operated on the mk th order. Assuming a linear response αω,k of the piezo actuator in the filter (filter k at frequency ω/(2π)), the refractive index n=1 in the FFP-TFs, and the spacing between the mirror surfaces of filter k at zero voltage d0,k=c/(2∙FSRk), the following two assumptions can be made: (i) The Fabry-Perot resonator length dk is linearly dependent on the applied piezo voltage Uk(t), yielding dk(Uk)=d0,k+α0,k∙U0,k+αω,k∙Ak∙sin(ωt-ϕk). (ii) The Fabry-Perot condition for constructive interference leads to λk(mk,t)=2dk/mk. Considering the first two filters, k=1 and k=2, in order to ensure optimum performance of the wavelength swept ASE source, the condition λ1(m1,t)=λ2(m2,t-τtrans-∆ϕR/ω) must be fulfilled for all times t. This directly translates to three equations that have to be satisfied simultaneously:
Equation (1) is equivalent to the fact that both center wavelengths λc,k(mk)=(2/mk) (d0,k+α0,k∙U0,k) must be matched, Eq. (2) implies equal full sweep ranges ∆λk(mk)=4αω,kAk/mk and Eq. (3) describes the condition for the phase delay. Considering only these three equations, for every combination of FFP orders m1 and m2, there is a solution yielding a desired λc and ∆λ. Nevertheless, since the piezo of the FFP-TF becomes nonlinear for too high input voltages, more conditions emerge that can make the problem unsolvable. Therefore, in order to avoid high U0,k or Ak, it can make sense to choose different orders mk if the FSRs of both filters at zero voltage are differing considerably. A rough estimation of the required accuracy for the filter parameter adjustment ensuring optimal operation is ~0.2° for ∆ϕ and ~0.2‰ of U0k and Ak.
In our setup, the FSR (zero voltage) of FFP-TF 1 was measured to be 22.2 THz, the FSR (zero voltage) of FFP-TF 2 was 27.2 THz. This difference is mainly compensated by matching the order m1=11 (FFP-TF 1) with the order m2=9 (FFP-TF 2). At a filter drive frequency fdrive=50 kHz, the DC voltages are U0,1=11.6 V and U0,2=10.5 V, yielding λc~1302 nm, the AC voltages A1=1.4 V and A2=0.9 V result in ∆λ=100 nm.
Due to thermal drift, non-linearity of the PZT and other parasitic effects, it is difficult to exactly predetermine all parameters to operate the source. Therefore, as startup procedure in our experiment, all parameters were optimized by slowly increasing the sweeping bandwidth while monitoring the power output of the source and the symmetry of both sweep directions.
3. Performance of the wavelength swept ASE source
3.1 Spectrum and output power
To demonstrate the good performance of the wavelength swept ASE source over a wide range of filter drive frequencies, we measured the interference signal (Fig. 1(b)) from a Mach-Zehnder interferometer with 0.5 mm arm length mismatch. The signals are plotted over one filter drive cycle (both sweep directions) for 5 kHz, 50 kHz and 170 kHz filter drive frequency at a full sweep range of 100 nm each. This corresponds to sweep rates of 2x5 kHz=10 kHz, 2x50 kHz=100 kHz and 2x170 kHz=340 kHz. The frequencies were chosen close to mechanical resonances of the filter to prevent heating and drift. In all cases, a average output powers of ~1.2 mW after FFP-TF 2 and 50 mW after the last isolator have been be achieved. In spite of the fact that the wavelength swept ASE source is critically sensitive to the setting of all filter drive parameters (see section 2), a stable operation could be observed for up to half an hour at 2x170 kHz and up to many hours at 2x5 kHz and 2x50 kHz. During this time, the ASE source could be used for imaging until filter drift effects led to a reduction of the output power and the sweeping bandwidth. Then a readjustment, mainly of the DC-voltage, was required. A closed feed-back loop to control the DC-voltage may enable stable, adjustment free operation at any frequency.
Figure 2(a) shows the spectrum of the wavelength swept ASE source at a filter drive frequency of 50 kHz and 100 nm full sweep width (50 mW average output power) measured with an optical spectrum analyzer (OSA). The broad background results from ASE, emitted by SOA 2. The sharp peak features at the edges of the spectrum are due to the non-linear, sinusoidal drive, they do not occur in the time traces (see Fig. 1(b)).
3.2 Required accuracy of the phase delay setting
In order to investigate the required accuracy of the phase delay between the filter drive waveforms, Fig. 2(b) shows the measured relative output power after FFP-TF 2 for different filter phase delay values ∆ϕF=∆ϕ+∆ϕR (red dots), being calculated from the difference in phase of the applied voltage ∆ϕ and the difference in filter phase response ∆ϕR . The power was averaged over one entire intensity trace, including forward (short to long wavelengths) and backward sweep. The full sweep range was 100 nm, the filter drive frequency 50 kHz. The mechanical phase response of both filters was measured at a drive frequency of 50 kHz with the method described in . We observed a difference in the phase response of ∆ϕR= −1.9°±0.4°. Figure 2(b) is corrected for the different mechanical response. Thus, the resulting curve has its maximum at ∆ϕF=1.6°±0.4° (∆ϕ=3.5° phase delay in applied voltage) which is in good agreement with Eq. (3). The transit time τtrans of light between the two filters is 102 ns in the setup, equivalent to 20.8 m of optical fiber or 1.8° phase shift at 50 kHz. This indicates that the phase shifted control of the two filters leads to an efficient operation by compensating light propagation effects. The full width at half maximum (FWHM) of the measured curve in Fig. 2 is 0.95° which implies a temporal width of 52.8 ns at 50 kHz. For a filter drive frequency of 5 kHz, this result translates to a temporal width of 528 ns, at 170 kHz of only 15.5 ns. The axis at the top of the graph shows the corresponding filter wavelength shift for a full sweep width of 100 nm assuming a mean filter sweep speed of 100 nm/10 µs (triangular, linear sweep). In order to obtain the theoretically expected drop of the average power (Fig. 2(b), black line), the instantaneous transmission spectra of both filters have to be convoluted with each other. For simplification, both spectra were measured only for those wavelengths providing the smallest instantaneous linewidths in the center of the sweep. The FWHM is 255 pm for FFP-TF 1 at 1330 nm and 284 pm for FFP-TF 2 at 1310 nm, yielding a FWHM of 516 pm (0.93°) after convolution. Good agreement with the measured data is observed. It should be noted that this is not the instantaneous linewidth (see chapter 4.3), but the sensitivity with respect to timing. The deviation between measurement and theory in Fig. 2(b), mainly in the wings of the curve, is probably due to an increase of the instantaneous linewidth and a decrease of the filter sweep speed towards the turning points of the filter, making the phase delay adjustment less critical. Thus, the edges of the spectrum make a dominant contribution to the average power in case of large phase detuning.
In summary, directly after FFP-TF 2, the acquired accuracy to set the delay time of the two filter drive signals is only determined by the properties of both filters (instantaneous linewidths) and the filter drive speed. After SOA 2, saturation effects also play a role, making the relative average power less critical to phase delay (~3° FWHM, 50 kHz). Nevertheless, for an optimum performance of the wavelength swept laser source, it is practical to optimize the drive parameters under consideration of the power after FFP-TF 2.
3.3 Instabilities and partial parasitic lasing at low frequencies
One feature of the demonstrated setup is the dual use of SOA 1, on the one hand as ASE source and on the other hand as a first amplification stage. This concept reduces the number of gain elements, no super luminescent diode (SLD) or additional SOA is required as primary broadband light source for seeding the amplification chain. Because of the dual use of SOA 1, saturation must be avoided to prevent a suppression of ASE light. Since in our case the typical average input power Pin to SOA 1 is about 10 µW, the small signal gain G is ~30 dB and the saturation power of the SOA is specified as 68 mW, saturation should be no problem for typical operation. The condition Pin∙G << Psat is fulfilled.
However, at low drive frequencies, we observed a characteristic feature that results from the double pass through SOA 1. The four traces in Fig. 3 show the transient optical power at different sweep frequencies over one filter drive cycle each (after the last isolator, acquired with a 150 MHz photo detector). Each trace corresponds to 100 nm full sweep width and an average output power of ~40 mW. In contrast to the filter drive at 50 kHz (Fig. 3(a)), the curve at 5 kHz (Fig. 3(b)) exhibits strong, parasitic modulations and high noise. At 1 kHz filter drive (Fig. 3(d)) the intensity modulation are even worse. In all three cases (A, B, D) the average input power Pin to SOA 1 is ~8 µW. The measurements show that the amplitude of
the power modulations is increasing with smaller wavelength sweep speed, slow sweeping causes higher noise. Besides the noise dependence on the filter drive speed, the observed noise also depends on the average input power Pin to SOA 1. A considerable reduction of the intensity modulations at 5 kHz drive can be achieved by reducing Pin to ~4 µW and increasing the amplification of SOA 2, in order to achieve the same output power (compare Fig. 3(c) and Fig. 3(b)). To analyze the origin of the observed instabilities, we calculated the Fourier spectrum of the noise. We observe broad maxima at ~10.3 MHz and ~11.1 MHz, for sweep rates of 2x1 kHz and 2x5 kHz, respectively. These values correspond very well with the optical path length of 18.4 m, which is the length from SOA 1 to the circulator (port 2), to the FFP-TF 1, to the polarization controller, to the circulator (port 3) and finally back to SOA 1. This observation implies that residual optical feedback from the back facet of SOA 1 causes a resonance. Since in the described circuit light experiences two amplifications by the SOA, the resulting total gain of up to 60 dB is high enough for partial parasitic lasing, considering typical SOA facet reflectivities of 10−5. Since the light passes through the filter, this partial parasitic lasing can only build up for very slow sweep rates of the filter, providing enough round trips. The effect is equivalent to the sweep rate limitation in standard swept laser sources . So, by reducing the gain in SOA 1, this partial parasitic lasing can be avoided. Also, for high sweep rates, the problem does not occur. Increasing the length of the described circuit will also reduce this effect by increasing the transit time. Then, the effect of parasitic lasing will occur at even lower frequencies.
4. Sensitivity and roll-off characteristics
4.1 Coherence and sensitivity
In order to investigate the coherence properties of the wavelength swept ASE source, the roll-off characteristics have been analyzed. We acquired interference signals with a dual balanced Mach-Zehnder interferometer for different delays at a filter drive frequency of 50 kHz and a full sweep range of 100 nm. The recorded fringe signals were Fourier transformed over forward sweeps (10 µs) after numerical resampling but without apodization and the resulting point spread functions (PSF) are plotted in Fig. 4(a) (lines) against OCT ranging depth, i.e. 0.5x the arm length mismatch of the Mach Zehnder interferometer. The logarithmic scale was adjusted such that the peak values correspond to the maximum achievable sensitivity in OCT application, assuming a lossless imaging setup and no power attenuation. The maximum sensitivity was determined to be 120.6 dB at a ranging depth of 0.25 mm for an average output power of 48 mW.
The red circles represent the drop of the interference contrast extracted from the interference signal envelope. No significant difference between forward and backward sweep could be observed. The maximum resolution (3 dB Gaussian fit) was measured to be ~12 µm in air, the dynamic range was ~50 dB.
4.2 Fringe visibility, optical phase noise and incoherent background
There are two remarkable features in Fig. 4(a). First, we can observe that neither the width of the PSFs nor the amount of side lobes change significantly over depth, even though the measurement range covers a total roll-off of ~40 dB. All PSFs appear sharp with negligible pedestal, only the amplitude decreases. It should be noted that the calibration signal for time to optical frequency resampling was only recorded once, before all the measurements. The fact that all PSFs are sharp even for long delays indicates that there is no drift, deviation, or low frequency oscillation on the evolution of the instantaneous center wavelength. Each sweep is very repeatable, the instantaneous wavelength does not jitter around the mean time dependent wavelength evolution, which can be the case in standard swept laser sources (random stepwise tuning). This fact may make the source highly suitable for any measurement, where an accurate knowledge of the center wavelength is required, like for fiber Bragg grating (FBG) sensing [20, 21].
The second observation in Fig. 4(a) is that at depths larger than ~3 mm, the red dots for the fringe visibility do not lie on the peaks of the PSFs. The roll-off over depth of the fringe visibility is significantly slower than for the PSFs. This is different from the situation found in standard wavelength swept lasers  or FDML lasers [31, 32], where over most of the measurement range the roll-off of the fringe visibility and the peaks of the PSFs is similar.
For the situation in the wavelength swept ASE source, we propose the following model. The considerations are similar to the more detailed analysis of intensity noise in [39,40], however, here we discuss the influence of phase noise. In our case, relative intensity noise is cancelled out by the dual balanced differential detection. The FWHM of the combined filters is ~0.18 nm, i.e. ~31 GHz optical linewidth at 1310 nm. This means, over a time of ~1/31 GHz=32 ps, phase and amplitude of the optical field are stable and can interfere. The optical field can be split and one part can be delayed by±16 ps with respect to the other field. If we consider the situation at a measurement depth of 5 mm (10 mm optical delay), the two optical fields are shifted by 33 ps with respect to each other and interfere. Due to the large temporal shift, there is no well defined phase relation between the two fields, however, the resulting, arbitrary phase difference stays constant for up to about 32 ps. If the dual balanced differential detector would be fast enough, a noise like signal with contributions up to 31 GHz would be observed. We can assume a flat noise spectrum from the SOA, so the measured noise power at the output of our 350 MHz detector will be approximately 31 GHz/350 MHz=89 times smaller, i.e. ~19 dB.
In a time domain picture, a signal is generated on the dual balanced differential detector by coherent contributions of the light field, incoherent background is cancelled. The coherence time is ~32 ps, i.e. the time over which a stable signal at the photodiode can be generated. After an average time of 32 ps, the phase relation is lost, that means every 32 ps another output value is measured at the photo-receiver. However, since the photodiodes and the detection system have an analog bandwidth of only 350 MHz, ~89 of these 32 ps intervals will be averaged incoherently. Because the signals of each of the 32 ps intervals have no phase relation, they add up incoherently and the voltage amplitude will be ~sqrt(89)=9.4, i.e. 19 dB lower than a coherent sum, like at short delays. This means a random signal amplitude with −19 dB will always remain at ranging depth longer than the instantaneous coherence length.
If we now compare the roll-off in fringe visibility for 0.25 mm ranging depth and 5.6 mm ranging depth, we observe 120.6 dB and 97.4 dB, respectively. The difference of 23.2 dB has the same order of magnitude than the calculated value above of ~19 dB, underlining the link between optical filter bandwidth, analog detection bandwidth and incoherent noise background. This means, applying a more narrowband filter will increase the instantaneous coherence length, but it will also increase the incoherent noise floor. This fact is important for the design of OCT and other coherent ranging systems, operated at the edge of the coherence performance of the applied light source.
The described link between instantaneous optical bandwidth and minimum noise floor should be universal and also applies to FDML lasers and conventional swept laser sources. However, in the case of lasers, the assumption of a white and flat noise background cannot always be made. Typically, in lasers higher noise at the cavity roundtrip frequency and the harmonics is observed. Even though the observed noise is usually relative intensity noise (RIN), phase noise and coherence properties might also be affected.
4.3 Improved performance by double filtering: reaching the shot noise limit
Another important feature of the wavelength swept ASE source is the advantage of an additional last filtering and amplification step, even though without it, setup and operation of the source would be even less complex. Therefore, in Fig. 4(b) the roll-off performance directly after the second pass through SOA 1 (maxima of PSFs, blue circles) is compared to the one of the wavelength swept ASE-source after FFP-TF 2 and SOA 2 (maxima of PSFs, black squares). The maxima of the PSFs represent the measured sensitivity. The maximum measured sensitivity of the wavelength swept ASE source after FFP-TF 2 and SOA 2 is 120.6 dB (48 mW). It exceeds the value obtained after SOA 1, which is measured to be 106.5 dB (0.25 mm OCT ranging depth) at 12 mW average output power. The shot noise limited sensitivity  for the wavelength swept ASE source after FFP-TF 2 and SOA 2 is 121.3 dB which is only 0.7 dB higher than the measured value. The theoretical value after SOA 1 is 115.4 dB which is 8.9 dB larger than the measured value. The observed difference is mainly due to the large ASE background directly after SOA 1, which contributes 80% of the total power, only 20% is coherent signal contribution. This discrepancy is due to the fact that with an input power of ~1 mW, SOA 2 is highly saturated, whereas the input power to SOA 1 (typically ~10 µW in our setup) is limited by the available power in the ASE spectrum and the narrow FWHM of the FFP-TF 1 transmission, preventing saturation. This means that the shot noise limit can only be reached with 2 SOAs and 2 filters, reducing ASE background.
In addition to higher power and reduced ASE background (yielding higher sensitivity), another advantage of using 2 filters is the improved coherence. At an imaging depth of 4 mm, a 7.5 dB difference in sensitivity is observed (Fig. 4(b)) due to the second filtering event. The blue dashed line (after SOA 1) and black solid line (after FFP-TF 2 and SOA 2) represent the roll-off expected from theory. They are calculated by a fast Fourier transform (FFT) of either the transmission spectrum of FFP-TF 1 (255 pm instantaneous linewidth (FWHM) at 1330 nm) or FFT of the product of both transmission spectra (FFP-TF 1 at 1330 nm and FFP-TF 2 at 1310 nm with an instantaneous linewidth (FWHM) of 180 pm). Good agreement with the measured data is observed, in particular for the operation after SOA 1. The deviation from the solid curve can be caused by a non-perfect drive parameter adjustment. Another possible explanation for the slight deviation of both curves is the increasing transmission bandwidth of the FFP-TFs towards the edges of the spectrum (e.g. 388 pm FWHM at 1250 nm vs. 255 pm FWHM at 1330 pm for FFP-TF 1), degrading the coherence properties. Due to the saturation of SOA 2, the relative power in the edges of the spectrum is increased compared to the spectrum after SOA 1. Thus, a larger instantaneous linewidth at the edges of the spectrum might have a larger influence on the coherence after SOA 2 than after SOA 1, explaining the higher deviation from the expected curve.
In summary, the measurements are indicating that the roll-off characteristics are only determined by the transmission spectra of the filters, if an optimum drive parameter setting is assumed. The roll-off of the demonstrated wavelength swept ASE source cannot match that of FDML operation, where multiple filtering events occur. The R-number (compare ) of the wavelength swept ASE source is determined to be 0.13 mm/dB (linear fit from 0.75 mm to 5.5 mm). For FDML lasers with comparable filter specifications and SOA gain media we reported R~0.3 mm/dB , R=1.4 mm/dB  and R~0.4 mm/dB . Nevertheless, the coherence properties are comparable to standard wavelength swept laser sources driven at high wavelength tuning speeds, where only the filter bandwidth determines the instantaneous coherence length . It may be sufficient for many applications, like OCT of the human retina, where a ranging depth of ~2 mm is sufficient. Furthermore, in order to push the roll-off performance, one or even two filters with a considerably narrower instantaneous transmission spectrum could be used instead, tolerating the resulting drawback of reduced output power. The requirement for the finesse of the filters would be relaxed, if two filters with narrow but slightly different FSR were used in order to achieve very narrow transmission bandwidth (Vernier tuning). Furthermore, the bandwidth of the first or alternatively the second filter may be increased, to make the phase adjustment less critical while still maintaining a narrow linewidth.
5. Relative Intensity Noise (RIN)
The RIN is a very important parameter to characterize light sources. The RIN properties are affecting the dynamic range in OCT application and may influence the image quality. RIN is the ratio of the standard deviation of the optical power δP over the mean optical power P. As described in , for periodically swept light sources, it is a reasonable and the most conservative way to analyze the power fluctuations between different sweeps at defined points in time (inter-sweep noise), rather than power fluctuations within one sweep over a sliding time window (intra-sweep noise). For the following measurements the optical power was measured with a photo detector (150 MHz analog bandwidth, Thorlabs), the resulting signal was lowpass filtered at 100 MHz and sampled with a 200 MSamples/s, 12 bit analog to digital converter card (ADC). 100 records, each consisting of 2000 samples, were acquired, each record covers one backward sweep. Thus, RIN (inter sweep noise) can be calculated for every sample in the record and hence assigned to individual wavelengths. The measured inter-sweep noise covers a bandwidth up to the system’s 100 MHz analog bandwidth .
For a better understanding of the differences, the RIN performance of the presented wavelength swept ASE source is directly compared to the RIN of an FDML laser. Up to now, a quantitative determination of RIN for FDML lasers has only been reported at 1550 nm . The FDML laser used for this comparison (1310 nm) was built in a sigma ring configuration. The complete laser, except for the delay line, consists of polarization maintaining (PM) fiber.
A PM version of the FFP-TF is used (LambdaQuest, LLC.). 30% of the power was coupled out between the SOA (Covega Corp.) and the delay line, 30% after the FFP-TF and the delay line. For the RIN analysis, the output after the SOA was analyzed. In order to match the operation parameters as well as possible, both, the FDML laser and the wavelength swept ASE source were driven at the fundamental FDML frequency of 54.6 kHz (2x bidirectional sweep duration of 9.2 µs) over a full sweep width of 100 nm and at a center wavelength of 1315 nm. The average output power of ~32 mW was attenuated to ~1.3 mW on the detector in both cases. For FDML operation, the choice of the accurate drive frequency is important for an optimum RIN performance. Thus, the RIN was measured over a frequency range of 600 Hz with a step size of 1 Hz. The frequency yielding the best RIN performance was chosen. When detuning the wavelength swept ASE source by several 10 Hz, the RIN is almost independent of the drive frequency; small differences are due to frequency dependent differences of the filter phase response (different filter phase delays). Here, the frequency with the highest average output power was chosen.
In Fig. 5 , the measured RIN value is plotted versus wavelength. The black line shows the RIN of the wavelength swept ASE source for a frequency of 54.680 kHz, the red line shows the RIN of the FDML laser at 54.574 kHz. The RIN value averaged over all wavelengths is 0.28% for the FDML laser and 1.33% for the wavelength swept ASE source. Obviously, the RIN performance of the FDML laser is exceeding that of the ASE source over the whole sweep spectrum, which is not surprising due to quasi-stationary operation in FDML . The average relative ratio of both RIN values is ~4.8, the smallest is found at 1310 nm with 1.7 and the largest value of ~14.3 is identified at the long wavelength side of the spectrum at 1365 nm. The reason for the strong increase in RIN of the wavelength swept ASE source at long wavelengths is unclear. It can be assumed that the last saturated amplification step in SOA 2 is considerably improving the RIN performance for the ASE source.
In standard wavelength swept lasers, RIN is considerably increasing with filter sweep speed [12, 30]. The RIN performance of the wavelength swept ASE source is comparable and may be even superior to standard wavelength swept lasers at high imaging speeds, because the lack of optical feedback prevents the appearance of a dominant noise at the laser cavity roundtrip frequency.
6. OCT imaging
To demonstrate the OCT imaging performance of the wavelength swept ASE source, Fig. 6 shows OCT images at a filter drive frequency of 50 kHz and a full sweep range of 100 nm. The input power into the OCT setup was ~30 mW resulting in an average power of 10 mW on the sample. The transversal resolution was ~17 µm, the measured sensitivity in the setup was ~110 dB. Signals from the detector were sampled at 400 MSamples/s with a 12 bit ADC. The data is numerically resampled for equidistant frequency spacing before the Fourier transform. Figure 6 shows 2D OCT-images (1024 lines, 5.4 mm) of the nail fold of a human finger in vivo (no averaging, Hanning apodized) (A), skin of a human finger (no averaging, Hanning apodized) (B) and a cucumber (10x averaged, Hanning apodized) (C). Figure 6(d) is a 3D reconstruction of an OCT data set of human skin (finger) consisting of 500 frames, 512 lines and 2000 axial pixels. The image quality is comparable to other high speed swept source OCT images. The images exhibit good contrast and penetration.
7. Conclusion and outlook
In conclusion, we presented an alternative approach to realize a rapidly wavelength swept light source for high-speed OCT imaging and sensing. A sequence of optical gain elements and tunable bandpass filters, which are driven with a defined phase delay, represent an optical circuit without feedback, overcoming physical limitations in sweep repetition rate. In analogy to FDML lasers, no fundamental limit to sweep speed exists, but in contrary, an operation over a continuous range of drive frequencies is possible. We demonstrated a wavelength swept ASE source at 1300 nm consisting of two SOA gain elements and two FFP-TF filter elements. We obtained an average output power of 50 mW. A full sweep range of 100 nm at 10 kHz, 100 kHz and 340 kHz sweep rate was achieved.
We showed that two filtering and amplification steps are necessary to achieve shot noise limited detection in OCT, to suppress ASE and to improve the coherence properties of the light source. We present a physical model for the connection between the optical filter bandwidth, the analog detection bandwidth and the observed incoherent background noise in OCT application. OCT imaging was demonstrated at 50 kHz line rate with good image quality, contrast and penetration.
In the future, the demonstrated technique may be attractive for swept light sources at 800 nm and 1060 nm, where high fiber loss and dispersion impede the realization of FDML lasers. Since no km long delay fiber is required, the wavelength swept ASE source might be very promising for ophthalmic high-speed SS-OCT. By optimizing the bandwidth of the different optical bandpass filters, the performance of the source may be further optimized. Non-equal values may be chosen to achieve good coherence properties and robust operation. Since the source appears to have extremely repeatable temporal tuning characteristics, it may be very suitable for sensing applications where a highly accurate measurement of spectral features is required, e.g. for fiber bragg grating sensors.
We would like to acknowledge support from Prof. W. Zinth at the Ludwig-Maximilians-University Munich. This research was sponsored by the Emmy Noether program of the German Research Foundation (DFG - HU 1006/2-1) and the European Union project FUN-OCT (FP7 HEALTH, contract no. 201880).
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