Abstract

Abstract: We propose a novel structure of complex-tap microwave photonic filter (MPF) employing an incoherent broadband optical source (BOS) and a programmable optical spectrum processor. By tailoring the optical spectral amplitude and phase, arbitrary complex continuous-time impulse responses of the MPF can be constructed. Frequency responses with a single flat-top, highly chirped, or arbitrary-shape passband are demonstrated, respectively. The passband center can also be tuned in a wide range only limited by the opto-electrical devices. To the best of our knowledge, it is the first demonstration of an incoherent-BOS-based MPF which is single-bandpass, widely tunable, and highly reconfigurable with complex taps.

© 2012 OSA

1. Introduction

Microwave photonic filters (MPFs) which process high-frequency microwave signals in the optical domain have aroused people’s great interest in the past decades [1]. The potential applications of MPFs include ultra-wideband radar, radio astronomy, high-speed microwave communications, etc. One important advantage of MPFs over their electrical counterparts is high reconfigurability. By tailoring the tap weights (or “coefficients”), flexible finite-impulse-response (FIR) MPFs can be implemented. For an ideal FIR MPF with full reconfigurability, each coefficient should be complex and can be adjusted arbitrarily. The direct way to implement complex-tap MPFs is to manipulate the microwave phase photonically in each tap. Various structures have been proposed in this scope based on the heterodyne method [26]. Single-sideband modulation (SSB) is employed, and the phase of the optical carrier is then adjusted. The optical phase change is translated to the microwave domain through heterodyning of the carrier with the sideband at the photodetector. Ideal complex taps can be generated, but the system complexity is high because wideband microwave 90° hybrid coupler or high-resolution optical spectrum processing is needed to implement SSB and optical carrier phase tuning. Another approximate method is using non-uniformly spaced optical carrier wavelengths [7]. By tuning the wavelength of each tap from the uniform position, an extra time delay is introduced to the microwave signal resulting in an equivalent phase shift. However, since the phase shift depends linearly on the microwave frequency, the complex tap is narrow-band. The function of the MPF is still limited.

In this paper, we propose a novel complex-tap MPF employing an incoherent broadband optical source (BOS) and a programmable optical spectrum processor. Equivalent “electrical slicing” of the BOS is employed [8], and complex coefficients are generated by tuning the localized slicing phase. It is worth noting that our structure looks similar to that in Refs [5, 6]. which uses coherent frequency combs. In comparison, our method has a reduced complexity since it only needs double-sideband suppressed-carrier (DSB-SC) modulation other than SSB. Furthermore, by taking advantage of low cost and spectral continuity of the BOS, arbitrary complex continuous-time impulse responses can be implemented, giving rise to a highly reconfigurable single passband in the frequency domain. The passband center can also be widely tuned by changing the slicing period. Differential detection is further employed to significantly reduce the optical intensity noise. To our knowledge, it is the first demonstration of a single-bandpass complex-tap MPF with high reconfigurability and wide tunability.

2. Experimental setup and theoretical description

Our experimental setup is shown in Fig. 1 . The incoherent light from a BOS (e.g. Erbium-doped fiber amplifier (EDFA) or light-emitting diode (LED)) is polarized and split into two branches via a 1 × 2 coupler (C1). One branch is modulated by the microwave input via a single-drive Mach-Zehnder modulator (MZM) biased at the minimum transport point. The other branch is spectrum tailored via a WaveShaper which is a commercial programmable optical processor [9], and time delayed via a variable optical delay line (VDL). The two branches are then combined again in the same polarization via a 2 × 2 coupler (C2). The two outputs of C2 go through a dispersive element which is a length of dispersion-compensating fiber (DCF) in opposite directions via two circulators and differentially detected.

 

Fig. 1 Setup of the fully reconfigurable single-bandpss MPF. BOS: incoherent broadband optical source; C: coupler; PC: polarization controller; MZM: Mach-Zehnder modulator; VDL: variable delay line; DCF: dispersion-compensating fiber; BPD: balanced photodetector.

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Under small-signal modulation, two sidebands are generated for each frequency component of the BOS in the MZM branch. When the sidebands are combined with the tailored carriers from the WaveShaper branch via C2, a 180°-shift is introduced in the sideband-carrier differential phase between the two outputs of C2. At the balanced photodetector (BPD), microwave signal currents are generated through beating of the sidebands with the corresponding carriers, and noise currents are generated mainly through beating of the carriers with each other. Thus the signals at the two inputs of the BPD are counter-phase while the noises are in-phase. The output of the BPD is given by subtraction of the two inputs. The total signal amplitude is then doubled while the noises are eliminated.

The WaveShaper is base on Liquid Crystal on Silicon (LCoS) technique, and acts as a programmable optical filter with arbitrary amplitude and phase responses [9]. The transfer function of the WaveShaper is denoted as HT(Ω)=AT(Ω)exp[jΦT(Ω)]. The microwave signal current at the output of the BPD is then [8]

iRFo(ω)=8l1l2[πVRFi/(4Vπ)]×12π0+N(Ω)AT(Ω)cos[ΩΔτΦT(Ω)θ2ω2/2]exp[jθ2(ΩΩ0)ω]dΩ,
where ω and Ω stand for the microwave and optical frequencies respectively, is the responsivity of the BPD, VRFi the microwave input amplitude, Vπ the half-wave voltage of the MZM, N(Ω) the single-side power spectral density (PSD) of the BOS at the input of C1, Δτ the time delay induced by the VDL, θ2 the total dispersion of the DCF (different from [8], θ2 is used here instead of β2 in case of confusion), Ω0 the central frequency of the BOS. l1and l2 represent the amplitude transmission factors from the input of C1 to the input of the BPD through the MZM branch and through the WaveShaper branch, respectively. The MPF’s transfer function is given by HRF(ω)=iRFo(ω)RL/VRFi where RL is the load resistant of the BPD. We can consider only the half part of HRF(ω) on the positive axis because HRF(ω)|ω0=HRF*(ω)|ω0. Suppose that Δτ/θ2>0 and the PSD of the BOS is constant with N(Ω)=N0, the MPF’s transfer function is then expressed as
H˜RF(ω)=HRF(ω)|ω0=RLN0l1l2/(2θ2Vπ)Hb(ωΔτ/θ2)exp[j(Ω0Δτθ2ω2/2)]
Here, Hb(ω) is the baseband function given by
Hb(ω)=θ20+HT*(Ω)exp[jθ2(ΩΩ0)ω]dΩ=[hb(t)]
where hb(t)=HT*(t/θ2+Ω0) the baseband complex impulse response which is a mapping of HT*(Ω) with t=θ2(ΩΩ0); []the Fourier transform. By programming the WaveShaper, arbitrary amplitude and phase of Hb(ω) can be achieved. By adjusting the VDL, Hb(ω)can be shifted to any frequency. Thus the MPF is both highly reconfigurable and widely tunable.

It is worth noting that hb(t) is continuous in time which means the MPF is a continuous-tap FIR filter, Hb(ω) can then be deliberately designed to be single-bandpass. The spectral continuity of BOS has long been exploited to implement single-bandpass MPFs [1012], and the concept of “continuous-time impulse response” was first proposed in Ref [12]. Nevertheless, the physical principle of complex tap generation in our scheme can be explained from the view of a discrete-tap MPF. As shown in Fig. 2 , the broadband optical spectrum is divided into many small sections. Each section corresponds to one tap, and acts as a photonic microwave phase shifter [13]. The RF output amplitude of each phase shifter can be adjusted by changing the optical amplitude while the phase adjusted by changing the localized slicing phase. By programming the WaveShaper, fully reconfigurable complex taps are generated.

 

Fig. 2 Illustration of complex tap generation.

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3. Experimental results and discussions

In experiments, we used a flat-gain EDFA as the BOS. The available spectral width was about 4 THz. The commercial WaveShaper had a spectral resolution of about 10 GHz. The total dispersion of the DCF was 1.71×10-21s2. The time resolution δt and aperture T of hb(t) are calculated to be 107 ps and 43.0 ns respectively. According to the Fourier transform theory, the reconfigurable spectral resolution and window width of the RF transfer function Hb(ω) are given by 1/T and 1/δτ which are 23.3 MHz and 9.31 GHz respectively. To demonstrate the flexible reconfigurability, the MPF’s passband was configured to be flat-top, chirped, or even with arbitrary shape, while the passband center was tuned to 6 GHz.

3.1. Flat-top MPF

For the flat-top MPF, the baseband time-domain impulse response is given by

hb(t)=sin(πBet)/(πBet)×WHann(t),T/2tT/2
where Be is the RF bandwidth, WHann(t) is the Hanning window function given by WHann(t)=0.5[1+cos(2πt/T)], T is the window width. In experiments, T was designed to be 21.5 ns. For Be=500MHz and 1GHz, the plots of hb(t), HT(Ω), and H˜RF(ω) are shown in Fig. 3(a)3(c) and 3(d)3(f), respectively. In Fig. 3(c) and 3(f), both measured and calculated results of H˜RF(ω) are shown, and they agree with each other quite well.

 

Fig. 3 hb(t), HT(Ω), and H˜RF(ω)for flat-top passbands with (a-c) Be=500MHz and (d-f) Be=1GHz. (In (c) and (f), solid: measured, dotted: calculated. See the context for the definition of symbols.)

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3.2. Chirped MPF

Chirped microwave filters are widely used in the pulse-compression technique. The baseband time-domain impulse response of the chirped MPF is given by

hb(t)=Wtanh(t)exp(jπt2/De),T/2tT/2
where De is the electrical dispersion in s/Hz, Wtanh(t) is the tanh window function given by Wtanh(t)=1+tanh[β(12|2t/T|α)] with α=β=3. In experiments, the MPF’s 3-dB bandwidth Be was designed to be 3 GHz. For De=5ns/GHz and 10ns/GHz, the plots of hb(t), HT(Ω), and H˜RF(ω) are shown in Fig. 4(a)4(c) and 4(d)4 (f), respectively. The optical and the electrical time delays follow the relationship |DeBe||θ2bo| where bo is the 3-dB bandwidth of AT(Ω) in rad/s. For specified Be and bo, higher De can be achieved by increasing the optical dispersion θ2.

 

Fig. 4 hb(t), HT(Ω), and H˜RF(ω) for chirped passbands with (a-c) Be=3GHz, De=5ns/GHz and (d-f) De=10ns/GHz. (In (c) and (f), solid: measured, dotted: calculated. See the context for the definition of symbols.)

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3.3. Arbitrary-shape MPF

To implement the arbitrary-shape MPF, hb(t)was digitally calculated from the desired Hb(ω) using inverse fast Fourier transform. For demonstration, Hb(ω) was designed to be an asymmetric trapezoid which is given by

20log(|Hb(ω)|)={30ω/ω1,ω1ω<00,0ωω2,others
where ω1~2GHz and ω2~1GHz. The phase of Hb(ω) is 0. It is noted that hb(t) is a complex function according the theory of Fourier transform. The plots of hb(t), HT(Ω), and H˜RF(ω) are shown in Fig. 5(a) - 5(c), respectively. Good agreements are obtained again between the measured and calculated results of H˜RF(ω) in Fig. 5(c).

 

Fig. 5 hb(t), HT(Ω), and H˜RF(ω) for arbitrary-shape passband. (In (c), solid: measured, dotted: calculated. See the context for the definition of symbols.)

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3.4. Tunability and noise reduction

The tunable amplitude responses of the flat-top MPF with Be=1GHz are shown in Fig. 6 . The time delay of the VDL needed for a RF bandpass center of ωc is given by Δτ=ωcθ2. Since the dispersion in this paper is twice that used in Ref [8], the required time delay range of the VDL for the same RF tuning range is doubled. Limited by the VDL we had at hand, only a range of 0~12GHzis shown here. However, by using an appropriate VDL, the RF bandpass center can be tuned in a wide range only limited by the opto-electrical devices.

 

Fig. 6 Tunable responses of the flat-top MPF with Be=1GHz.

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We then investigated the noise-reduction performance of the balanced detection scheme. For simplicity, HT(Ω) was programmed to be a rectangle with a bandwidth of 0.6 THz, thus Hb(ω) was a sinc function. The passband center was tuned to 10 GHz. The responsivity of the BPD was 0.7 A/W, and the optical power at each input was 8dBm. The RF input signal was a single tone of 10 GHz. The intensity modulation index is calculated from the measured sideband-to-carrier ratio (SCR) according to m=4(SCR)1/2, by replacing the BOS with a single-wavelength laser. It has been investigated that the modulation-induced noise increment forms a basic limit to the performance of balanced detection [14]. The RF output spectra with balanced detection or with only one single input of the BPD are shown in Fig. 7(a) and 7(b). An obvious increment of the noise ground level with increasing mcan be observed when balanced detection is employed. Detailed plots of the signal and noise power versus m are shown in Fig. 7(c). When m<0.2, the noise reduction is limited by the unbalance of the two optical paths denoted in Fig. 1 by doted arrows. This unbalance in our experiments is mainly attributed to the polarization dependent loss and dispersion. In this region, an improvement of the signal-to-noise ratio (SNR) of roughly 14 dB can be achieved. When m>0.2, the noise power increases with m. The noise reduction is 5 dB when m=0.43corresponding to a root-mean-square value of 0.3. The result agrees with the theoretical prediction in Ref [14]. quite well. It is noteworthy that a SNR increment of 11 dB is still achieved at this point because the RF signal power is 6 dB higher with balanced detection than that with one single input.

 

Fig. 7 (a), (b) RF output spectra and (c) plots of signal and noise power versus modulation index (the noise bandwidth equals the RF spectrum analyzer’s RBW which is 3 MHz).

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4. Conclusions

In conclusion, we have proposed a novel complex-tap MPF employing a low-cost incoherent BOS and a commercial optical spectrum processor. The MPF’s transfer function was single-bandpass, widely tunable, and highly reconfigurable. Frequency responses with a flat-top, highly chirped, or arbitrary-shape passband were demonstrated, respectively.

Acknowledgments

This work is supported by the 973 Project under grant Nos. 2012CB315603/04, China Postdoctoral Science Foundation under grant No. 2012M520275, and National Nature Science Foundation of China (NSFC) under grant Nos. 60736003, 61025004, and 61032005.

References and links

1. J. Capmany, B. Ortega, and D. Pastor, “A tutorial on microwave photonic filters,” J. Lightwave Technol. 24(1), 201–229 (2006). [CrossRef]  

2. A. Loayssa, J. Capmany, M. Sagues, and J. Mora, “Demonstration of incoherent microwave photonic filters with all-optical complex coefficients,” IEEE Photon. Technol. Lett. 18(16), 1744–1746 (2006). [CrossRef]  

3. M. Sagues, R. García Olcina, A. Loayssa, S. Sales, and J. Capmany, “Multi-tap complex-coefficient incoherent microwave photonic filters based on optical single-sideband modulation and narrow band optical filtering,” Opt. Express 16(1), 295–303 (2008). [CrossRef]   [PubMed]  

4. X. Yi, T. X. H. Huang, and R. A. Minasian, “Tunable and reconfigurable photonic signal processor with programmable all-optical complex coefficients,” IEEE Trans. Microw. Theory Tech. 58(11), 3088–3093 (2010).

5. E. Hamidi, D. E. Leaird, and A. M. Weiner, “Tunable programmable microwave photonic filters based on an optical frequency comb,” IEEE Trans. Microw. Theory Tech. 58(11), 3269–3278 (2010). [CrossRef]  

6. M. Song, C. M. Long, R. Wu, D. Seo, D. E. Leaird, and A. M. Weiner, “Reconfigurable and tunable flat-top microwave photonic filters utilizing optical frequency combs,” IEEE Photon. Technol. Lett. 23(21), 1618–1620 (2011). [CrossRef]  

7. Y. Dai and J. Yao, “Nonuniformly spaced photonic microwave delay-line filters and applications,” IEEE Trans. Microw. Theory Tech. 58(11), 3279–3289 (2010). [CrossRef]  

8. X. Xue, X. Zheng, H. Zhang, and B. Zhou, “Widely tunable single-bandpass microwave photonic filter employing a non-sliced broadband optical source,” Opt. Express 19(19), 18423–18429 (2011). [CrossRef]   [PubMed]  

9. Finisar Corporation, “Programmable narrow-band filtering using the WaveShaper 1000E and WaveShaper 4000E,” product whitepaper.

10. J. Mora, B. Ortega, A. Díez, J. L. Cruz, M. V. Andrés, J. Capmany, and D. Pastor, “Photonic microwave tunable single-bandpass filter based on a Mach–Zehnder interferometer,” J. Lightwave Technol. 24(7), 2500–2509 (2006). [CrossRef]  

11. J. H. Lee and Y. M. Chang, “Detailed theoretical and experimental study on single passband, photonic microwave FIR filter using digital micromirror device and continuous-wave supercontinuum,” J. Lightwave Technol. 26(15), 2619–2628 (2008). [CrossRef]  

12. T. X. Huang, X. Yi, and R. A. Minasian, “Single passband microwave photonic filter using continuous-time impulse response,” Opt. Express 19(7), 6231–6242 (2011). [CrossRef]   [PubMed]  

13. X. Xue, X. Zheng, H. Zhang, and B. Zhou, “All-optical microwave bandpass filter and phase shifter using a broadband optical source and an optical phase modulator,” Opt. Lett. 37(10), 1661–1663 (2012). [CrossRef]   [PubMed]  

14. T. E. Darcie and A. Moye, “Modulation-dependent limits to intensity-noise suppression in microwave-photonic links,” IEEE Photon. Technol. Lett. 17(10), 2185–2187 (2005). [CrossRef]  

References

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  1. J. Capmany, B. Ortega, and D. Pastor, “A tutorial on microwave photonic filters,” J. Lightwave Technol.24(1), 201–229 (2006).
    [CrossRef]
  2. A. Loayssa, J. Capmany, M. Sagues, and J. Mora, “Demonstration of incoherent microwave photonic filters with all-optical complex coefficients,” IEEE Photon. Technol. Lett.18(16), 1744–1746 (2006).
    [CrossRef]
  3. M. Sagues, R. García Olcina, A. Loayssa, S. Sales, and J. Capmany, “Multi-tap complex-coefficient incoherent microwave photonic filters based on optical single-sideband modulation and narrow band optical filtering,” Opt. Express16(1), 295–303 (2008).
    [CrossRef] [PubMed]
  4. X. Yi, T. X. H. Huang, and R. A. Minasian, “Tunable and reconfigurable photonic signal processor with programmable all-optical complex coefficients,” IEEE Trans. Microw. Theory Tech.58(11), 3088–3093 (2010).
  5. E. Hamidi, D. E. Leaird, and A. M. Weiner, “Tunable programmable microwave photonic filters based on an optical frequency comb,” IEEE Trans. Microw. Theory Tech.58(11), 3269–3278 (2010).
    [CrossRef]
  6. M. Song, C. M. Long, R. Wu, D. Seo, D. E. Leaird, and A. M. Weiner, “Reconfigurable and tunable flat-top microwave photonic filters utilizing optical frequency combs,” IEEE Photon. Technol. Lett.23(21), 1618–1620 (2011).
    [CrossRef]
  7. Y. Dai and J. Yao, “Nonuniformly spaced photonic microwave delay-line filters and applications,” IEEE Trans. Microw. Theory Tech.58(11), 3279–3289 (2010).
    [CrossRef]
  8. X. Xue, X. Zheng, H. Zhang, and B. Zhou, “Widely tunable single-bandpass microwave photonic filter employing a non-sliced broadband optical source,” Opt. Express19(19), 18423–18429 (2011).
    [CrossRef] [PubMed]
  9. Finisar Corporation, “Programmable narrow-band filtering using the WaveShaper 1000E and WaveShaper 4000E,” product whitepaper.
  10. J. Mora, B. Ortega, A. Díez, J. L. Cruz, M. V. Andrés, J. Capmany, and D. Pastor, “Photonic microwave tunable single-bandpass filter based on a Mach–Zehnder interferometer,” J. Lightwave Technol.24(7), 2500–2509 (2006).
    [CrossRef]
  11. J. H. Lee and Y. M. Chang, “Detailed theoretical and experimental study on single passband, photonic microwave FIR filter using digital micromirror device and continuous-wave supercontinuum,” J. Lightwave Technol.26(15), 2619–2628 (2008).
    [CrossRef]
  12. T. X. Huang, X. Yi, and R. A. Minasian, “Single passband microwave photonic filter using continuous-time impulse response,” Opt. Express19(7), 6231–6242 (2011).
    [CrossRef] [PubMed]
  13. X. Xue, X. Zheng, H. Zhang, and B. Zhou, “All-optical microwave bandpass filter and phase shifter using a broadband optical source and an optical phase modulator,” Opt. Lett.37(10), 1661–1663 (2012).
    [CrossRef] [PubMed]
  14. T. E. Darcie and A. Moye, “Modulation-dependent limits to intensity-noise suppression in microwave-photonic links,” IEEE Photon. Technol. Lett.17(10), 2185–2187 (2005).
    [CrossRef]

2012

2011

2010

Y. Dai and J. Yao, “Nonuniformly spaced photonic microwave delay-line filters and applications,” IEEE Trans. Microw. Theory Tech.58(11), 3279–3289 (2010).
[CrossRef]

X. Yi, T. X. H. Huang, and R. A. Minasian, “Tunable and reconfigurable photonic signal processor with programmable all-optical complex coefficients,” IEEE Trans. Microw. Theory Tech.58(11), 3088–3093 (2010).

E. Hamidi, D. E. Leaird, and A. M. Weiner, “Tunable programmable microwave photonic filters based on an optical frequency comb,” IEEE Trans. Microw. Theory Tech.58(11), 3269–3278 (2010).
[CrossRef]

2008

2006

2005

T. E. Darcie and A. Moye, “Modulation-dependent limits to intensity-noise suppression in microwave-photonic links,” IEEE Photon. Technol. Lett.17(10), 2185–2187 (2005).
[CrossRef]

Andrés, M. V.

Capmany, J.

Chang, Y. M.

Cruz, J. L.

Dai, Y.

Y. Dai and J. Yao, “Nonuniformly spaced photonic microwave delay-line filters and applications,” IEEE Trans. Microw. Theory Tech.58(11), 3279–3289 (2010).
[CrossRef]

Darcie, T. E.

T. E. Darcie and A. Moye, “Modulation-dependent limits to intensity-noise suppression in microwave-photonic links,” IEEE Photon. Technol. Lett.17(10), 2185–2187 (2005).
[CrossRef]

Díez, A.

García Olcina, R.

Hamidi, E.

E. Hamidi, D. E. Leaird, and A. M. Weiner, “Tunable programmable microwave photonic filters based on an optical frequency comb,” IEEE Trans. Microw. Theory Tech.58(11), 3269–3278 (2010).
[CrossRef]

Huang, T. X.

Huang, T. X. H.

X. Yi, T. X. H. Huang, and R. A. Minasian, “Tunable and reconfigurable photonic signal processor with programmable all-optical complex coefficients,” IEEE Trans. Microw. Theory Tech.58(11), 3088–3093 (2010).

Leaird, D. E.

M. Song, C. M. Long, R. Wu, D. Seo, D. E. Leaird, and A. M. Weiner, “Reconfigurable and tunable flat-top microwave photonic filters utilizing optical frequency combs,” IEEE Photon. Technol. Lett.23(21), 1618–1620 (2011).
[CrossRef]

E. Hamidi, D. E. Leaird, and A. M. Weiner, “Tunable programmable microwave photonic filters based on an optical frequency comb,” IEEE Trans. Microw. Theory Tech.58(11), 3269–3278 (2010).
[CrossRef]

Lee, J. H.

Loayssa, A.

M. Sagues, R. García Olcina, A. Loayssa, S. Sales, and J. Capmany, “Multi-tap complex-coefficient incoherent microwave photonic filters based on optical single-sideband modulation and narrow band optical filtering,” Opt. Express16(1), 295–303 (2008).
[CrossRef] [PubMed]

A. Loayssa, J. Capmany, M. Sagues, and J. Mora, “Demonstration of incoherent microwave photonic filters with all-optical complex coefficients,” IEEE Photon. Technol. Lett.18(16), 1744–1746 (2006).
[CrossRef]

Long, C. M.

M. Song, C. M. Long, R. Wu, D. Seo, D. E. Leaird, and A. M. Weiner, “Reconfigurable and tunable flat-top microwave photonic filters utilizing optical frequency combs,” IEEE Photon. Technol. Lett.23(21), 1618–1620 (2011).
[CrossRef]

Minasian, R. A.

T. X. Huang, X. Yi, and R. A. Minasian, “Single passband microwave photonic filter using continuous-time impulse response,” Opt. Express19(7), 6231–6242 (2011).
[CrossRef] [PubMed]

X. Yi, T. X. H. Huang, and R. A. Minasian, “Tunable and reconfigurable photonic signal processor with programmable all-optical complex coefficients,” IEEE Trans. Microw. Theory Tech.58(11), 3088–3093 (2010).

Mora, J.

A. Loayssa, J. Capmany, M. Sagues, and J. Mora, “Demonstration of incoherent microwave photonic filters with all-optical complex coefficients,” IEEE Photon. Technol. Lett.18(16), 1744–1746 (2006).
[CrossRef]

J. Mora, B. Ortega, A. Díez, J. L. Cruz, M. V. Andrés, J. Capmany, and D. Pastor, “Photonic microwave tunable single-bandpass filter based on a Mach–Zehnder interferometer,” J. Lightwave Technol.24(7), 2500–2509 (2006).
[CrossRef]

Moye, A.

T. E. Darcie and A. Moye, “Modulation-dependent limits to intensity-noise suppression in microwave-photonic links,” IEEE Photon. Technol. Lett.17(10), 2185–2187 (2005).
[CrossRef]

Ortega, B.

Pastor, D.

Sagues, M.

M. Sagues, R. García Olcina, A. Loayssa, S. Sales, and J. Capmany, “Multi-tap complex-coefficient incoherent microwave photonic filters based on optical single-sideband modulation and narrow band optical filtering,” Opt. Express16(1), 295–303 (2008).
[CrossRef] [PubMed]

A. Loayssa, J. Capmany, M. Sagues, and J. Mora, “Demonstration of incoherent microwave photonic filters with all-optical complex coefficients,” IEEE Photon. Technol. Lett.18(16), 1744–1746 (2006).
[CrossRef]

Sales, S.

Seo, D.

M. Song, C. M. Long, R. Wu, D. Seo, D. E. Leaird, and A. M. Weiner, “Reconfigurable and tunable flat-top microwave photonic filters utilizing optical frequency combs,” IEEE Photon. Technol. Lett.23(21), 1618–1620 (2011).
[CrossRef]

Song, M.

M. Song, C. M. Long, R. Wu, D. Seo, D. E. Leaird, and A. M. Weiner, “Reconfigurable and tunable flat-top microwave photonic filters utilizing optical frequency combs,” IEEE Photon. Technol. Lett.23(21), 1618–1620 (2011).
[CrossRef]

Weiner, A. M.

M. Song, C. M. Long, R. Wu, D. Seo, D. E. Leaird, and A. M. Weiner, “Reconfigurable and tunable flat-top microwave photonic filters utilizing optical frequency combs,” IEEE Photon. Technol. Lett.23(21), 1618–1620 (2011).
[CrossRef]

E. Hamidi, D. E. Leaird, and A. M. Weiner, “Tunable programmable microwave photonic filters based on an optical frequency comb,” IEEE Trans. Microw. Theory Tech.58(11), 3269–3278 (2010).
[CrossRef]

Wu, R.

M. Song, C. M. Long, R. Wu, D. Seo, D. E. Leaird, and A. M. Weiner, “Reconfigurable and tunable flat-top microwave photonic filters utilizing optical frequency combs,” IEEE Photon. Technol. Lett.23(21), 1618–1620 (2011).
[CrossRef]

Xue, X.

Yao, J.

Y. Dai and J. Yao, “Nonuniformly spaced photonic microwave delay-line filters and applications,” IEEE Trans. Microw. Theory Tech.58(11), 3279–3289 (2010).
[CrossRef]

Yi, X.

T. X. Huang, X. Yi, and R. A. Minasian, “Single passband microwave photonic filter using continuous-time impulse response,” Opt. Express19(7), 6231–6242 (2011).
[CrossRef] [PubMed]

X. Yi, T. X. H. Huang, and R. A. Minasian, “Tunable and reconfigurable photonic signal processor with programmable all-optical complex coefficients,” IEEE Trans. Microw. Theory Tech.58(11), 3088–3093 (2010).

Zhang, H.

Zheng, X.

Zhou, B.

IEEE Photon. Technol. Lett.

M. Song, C. M. Long, R. Wu, D. Seo, D. E. Leaird, and A. M. Weiner, “Reconfigurable and tunable flat-top microwave photonic filters utilizing optical frequency combs,” IEEE Photon. Technol. Lett.23(21), 1618–1620 (2011).
[CrossRef]

A. Loayssa, J. Capmany, M. Sagues, and J. Mora, “Demonstration of incoherent microwave photonic filters with all-optical complex coefficients,” IEEE Photon. Technol. Lett.18(16), 1744–1746 (2006).
[CrossRef]

T. E. Darcie and A. Moye, “Modulation-dependent limits to intensity-noise suppression in microwave-photonic links,” IEEE Photon. Technol. Lett.17(10), 2185–2187 (2005).
[CrossRef]

IEEE Trans. Microw. Theory Tech.

Y. Dai and J. Yao, “Nonuniformly spaced photonic microwave delay-line filters and applications,” IEEE Trans. Microw. Theory Tech.58(11), 3279–3289 (2010).
[CrossRef]

X. Yi, T. X. H. Huang, and R. A. Minasian, “Tunable and reconfigurable photonic signal processor with programmable all-optical complex coefficients,” IEEE Trans. Microw. Theory Tech.58(11), 3088–3093 (2010).

E. Hamidi, D. E. Leaird, and A. M. Weiner, “Tunable programmable microwave photonic filters based on an optical frequency comb,” IEEE Trans. Microw. Theory Tech.58(11), 3269–3278 (2010).
[CrossRef]

J. Lightwave Technol.

Opt. Express

Opt. Lett.

Other

Finisar Corporation, “Programmable narrow-band filtering using the WaveShaper 1000E and WaveShaper 4000E,” product whitepaper.

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Figures (7)

Fig. 1
Fig. 1

Setup of the fully reconfigurable single-bandpss MPF. BOS: incoherent broadband optical source; C: coupler; PC: polarization controller; MZM: Mach-Zehnder modulator; VDL: variable delay line; DCF: dispersion-compensating fiber; BPD: balanced photodetector.

Fig. 2
Fig. 2

Illustration of complex tap generation.

Fig. 3
Fig. 3

h b (t) , H T (Ω) , and H ˜ RF (ω) for flat-top passbands with (a-c) B e =500 MHz and (d-f) B e =1 GHz . (In (c) and (f), solid: measured, dotted: calculated. See the context for the definition of symbols.)

Fig. 4
Fig. 4

h b (t) , H T (Ω) , and H ˜ RF (ω) for chirped passbands with (a-c) B e =3 GHz , D e =5 ns/GHz and (d-f) D e =10 ns/GHz . (In (c) and (f), solid: measured, dotted: calculated. See the context for the definition of symbols.)

Fig. 5
Fig. 5

h b (t) , H T (Ω) , and H ˜ RF (ω) for arbitrary-shape passband. (In (c), solid: measured, dotted: calculated. See the context for the definition of symbols.)

Fig. 6
Fig. 6

Tunable responses of the flat-top MPF with B e =1 GHz .

Fig. 7
Fig. 7

(a), (b) RF output spectra and (c) plots of signal and noise power versus modulation index (the noise bandwidth equals the RF spectrum analyzer’s RBW which is 3 MHz).

Equations (5)

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i RFo ( ω )=8 l 1 l 2 [ π V RFi / ( 4 V π ) ]× 1 2π 0 + N( Ω ) A T ( Ω ) cos[ ΩΔτ Φ T ( Ω ) θ 2 ω 2 /2 ]exp[ j θ 2 ( Ω Ω 0 )ω ] dΩ,
H b ( ω )= θ 2 0 + H T * ( Ω )exp[ j θ 2 ( Ω Ω 0 )ω ] dΩ =[ h b ( t ) ]
h b ( t )= sin( π B e t ) / ( π B e t ) × W Hann ( t ), T/2 tT/2
h b ( t )= W tanh ( t )exp( jπ t 2 / D e ), T/2 tT/2
20log( | H b ( ω ) | )={ 30ω / ω 1 , ω 1 ω<0 0, 0ω ω 2 , others

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